Method and apparatus for generating a common-mode reference signal

ABSTRACT

A method and apparatus to generate a common-mode reference signal. A common-mode current is received at a common-mode current sensing circuit. The common-mode current is sampled at a node between the common-mode current sensing circuit and a shunt resistor. The resulting voltage across the shunt resistor from the applied common-mode current is used as a common-mode reference signal.

CROSS-REFERENCE TO PENDING APPLICATIONS

This application is a divisional application of U.S. patent applicationSer. No. 12/290,546 filed Oct. 30, 2008 entitled “Method and ApparatusFor Generating A Common-Mode Reference Signal” which is herebyincorporated by reference in its entirety.

BACKGROUND OF THE INVENTION

1. Field of the Invention

This invention relates to the field of telecommunications systems and,in particular, to common-mode noise cancellation in a telecommunicationssystem.

2. Prior Art

Many modem communications systems employ a twisted wire pair usingdifferential signaling to transmit data. Among the communicationssystems in this category are telecommunications systems such as thevarious types of Digital Subscriber Line (xDSL), and other digitalcarrier systems. xDSL may include, for example, asymmetric digitalsubscriber line (ADSL), asymmetric digital subscriber line two plus(ADSL2+) and very high-speed digital subscriber line (VDSL) systems.

In ADSL2+ modems with a frequency range of 138 kilohertz (KHz) to 2.2megahertz (MHz), the signal-to-noise ratio (SNR) is often degraded bythe presence of radio and other unwanted signals that are inadvertentlypicked up by the system. In particular, AM radio signals in the range of540 KHz to 1.6 MHz may cause significant interference. In VDSL moderns,with an upper frequency of 12 MHz to 17 MHz, there are even moredisturber sources that can corrupt the SNR.

These unwanted signals are impressed on the twisted pair line as acommon-mode signal with respect to ground. In conventional xDSL modems,receivers are designed to accept differential signals and reject commonmode signals. The modems typically include a common mode filter toreject a substantial portion of the common mode signal. Depending on thequality and balance of the twisted pair line, some portion of thecommon-mode signal may be converted to a differential signal in the lineitself. Under typical conditions, this portion may be enough to limitsystem performance.

Once converted to a differential signal by any means, the disturbersignal appears as noise mixed with the intended communication signal andthis effectively degrades the SNR and hence the data throughputperformance of the modem. If the common-mode noise signal Y is knownindependently of the signal X+Y that contains both noise signal Y anddifferential communication signal X, then it is possible for the modem,using digital signal processing (DSP) means, to subtract the signal Yfrom the signal X+Y and be left with just the signal X. In other words,it is possible to uncover the intended communication signal in thepresence of the common-mode noise signal.

In order to support DSP cancellation of the common-mode signals in anxDSL modem, two additional functional blocks are required in hardware:(1) a second receiver input containing an analog-to-digital converter(ADC): and (2) a circuit to generate a common-mode reference signalwhich contains substantially only the common-mode content of the line.

FIG. 1 illustrates a conventional common-mode reference signalgeneration circuit. In FIG. 1, the noise estimate is based on acommon-mode reference noise signal, which is sampled via an additionalwinding on the magnetic core of the common mode filter inductor thatcouples the input lines to the receiver. Existing communicationstandards require that the primary winding or windings of the linetransformer or filter inductor be isolated from chassis ground and fromthe secondary winding. A common-mode reference signal detector must spanand yet provide galvanic isolation between the telecom network voltage(TNV) circuitry and the safe effective low voltage (SELV) circuitry. Thebreakdown voltage of this isolation must be at least 1500 volts ofalternating current (VAC). Therefore, a common-mode reference noisesignal, either from the center tap of the primary winding of the linecoupling transformer or from an additional winding on the common modefilter inductor (as shown in FIG. 1) cannot be connected directly to theradio frequency (RF) noise canceller. Isolation by means of and anadditional and more costly high-voltage transformer is required.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention is illustrated by way of example, and not by wayof limitation, in the figures of the accompanying drawings.

FIG. 1 illustrates a conventional common-mode reference signalgeneration circuit.

FIG. 2A illustrates a block diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 2B illustrates a block diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 3 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

FIG. 4 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 5 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

FIG. 6 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 7 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 8 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

FIG. 9 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.

FIG. 10 illustrates a schematic diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

FIG. 11 illustrates a schematic diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

FIG. 12 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

The following description sets forth numerous specific details such asexamples of specific systems, components, methods, and so forth, inorder to provide a good understanding of several embodiments of thepresent invention. It will be apparent to one skilled in the art,however, that at least some embodiments of the present invention may bepracticed without these specific details. In other instances, well-knowncomponents or methods are not described in detail or are presented insimple block diagram format in order to avoid unnecessarily obscuringthe present invention. Thus, the specific details set forth are merelyexemplary. Particular implementations may vary from these exemplarydetails and still be contemplated to be within the scope of the presentinvention.

Embodiments of a method and apparatus are described to generate acommon-mode reference signal. In one embodiment, a common-mode currentis received at a common-mode current sensing circuit. The common-modecurrent is then sampled at a node between the common-mode filter sourceand a shunt resistor. The resulting voltage across the shunt resistorfrom the applied common-mode current is used as a common-mode referencesignal.

FIG. 2A illustrates a block diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.Circuit 200A includes twisted pair 203, common-mode current sensingcircuit 215, output node 240, shunt resistor 250, low supply node 260,receivers 271 and 272 and noise canceller 275. Common-mode currentsensing circuit 215 is coupled to twisted pair 203 and is configured toreceive a common-mode current. As will be discussed below, common-modecurrent sensing circuit 215 may receive the common-mode current directlyfrom the twisted pair 203 or from the center tap of a transformer (notshown). The common-mode current sensing circuit 215 draws thecommon-mode current and provides it to output node 240. The common-modecurrent is applied to shunt resistor 250 which is coupled between outputnode 240 and a low supply node 260. The resulting voltage at output node240 is used as a common-mode reference signal.

The first receiver 271 receives the combined differential andcommon-mode signal from twisted pair 203. The common-mode referencesignal at output node 240 is applied to a second receiver 272. Receivers271 and 272 provide their respective signals to noise canceller 275. Atnoise canceller 275, the common-mode reference signal is subtracted fromthe combined signal. The output of noise canceller 275 is thedifferential signal containing the communication data with minimalinterference from the common-mode noise signal.

FIG. 2B illustrates a block diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.In circuit 200B twisted pair 203 contains both differential data signalsand common-mode noise signals attributable to interference sources whichradiate onto twisted pair 203 resulting in the noise signals. Forexample, the interference sources may be AM radio waves in the range of540 KHz to 1.6 MHz. Alternatively, the interference may be caused byother sources. In one embodiment, the signals from twisted pair 203 areapplied to common-mode filter 210. Common-mode filter 210 serves tofilter out the common-mode noise, however, common-mode noise filter 210may not remove all common-mode noise. The remaining noise signals areprovided to 2 to 4 wire converter 220. In one embodiment converter 220is a transformer having a center tap on an input side. The center tap iscoupled to common-mode current sensing circuit 216 via connection 214.In this embodiment, connection 213 is not present. In an alternativeembodiment, twisted pair 203 provides the common-mode current directlyto common-mode current sensing circuit 216 via connection 213. In thisalternative embodiment, connection 214 is not present.

In either embodiment, common-mode current sensing circuit provides thecommon-mode current to output node 240. The common-mode current isapplied to shunt resistor 250 which is coupled between output node 240and a low supply node 260. The resulting voltage at output node 240 isused as a common-mode reference signal which is provided to receiver272. Receiver 271 receives the combined differential and common-modesignal from twisted pair 203. Receivers 271 and 272 provide theirrespective signals to noise canceller 275. In one embodiment receivers271 and 272 are differential receivers each having two inputs. Receiver271 is coupled to and receives two outputs from 2 to 4 wire converter220. Receiver 272 has one input coupled to output node 240 and a secondinput coupled to ground. In an alternative embodiment, the second inputof receiver 272 is coupled to ground through a DC blocking capacitor. Inalternative embodiments, the inputs of receivers 271 and 272 areconnected in other ways. At noise canceller 275, the common-modereference signal is subtracted from the combined signal. The output ofnoise canceller 275 is the differential signal containing thecommunication data with minimal interference from the common-mode noisesignal.

FIG. 3 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. In this embodiment, circuit 300 includes input lines 301 and302, series windings 311 and 312, transformer 320, center tap potentialfeed circuit 330, output node 340, shunt resistor 350, low supply node360 and receivers 371 and 372. The first series winding 311 is coupledto the first input line 301 and is configured to receive a first inputsignal. The second series winding 312 is coupled to the second inputline 302 and is configured to receive a second signal. At the endopposite the first input line 301, the first series winding 311 iscoupled to one end of an input winding of transformer 320. Similarly,the second series winding 312 is coupled to a second end of the inputwinding of transformer 320. In one embodiment, series windings 311 and312 are two windings on a common core, wired in an arrangement thatgenerates a magnetic field only to common-mode signals, where one is inseries with each of the incoming lines. An output winding of transformer320 is coupled to a first receiver 371.

In this embodiment, the common-mode current is obtained from transformer320 through center tap 325. Center tap potential feed circuit 330 iscoupled to center tap 325 and receives the common-mode current. Theoutput of center tap potential feed circuit 330 is coupled to outputnode 340. Output node 340 is further coupled to a low supply node 360through shunt resistor 350. In this embodiment, low supply node 360 hasa ground potential and shunt resistor 350 has a resistance inapproximately a range of 10 ohms to 500 ohms. In alternative embodimentsshunt resistor 350 has some other resistance value. In other alternativeembodiments, low supply node 360 has some other low potential value.Also connected to output node 340 is a second receiver 372. Both thefirst receiver 371 and the second receiver 372 are referenced to ground.

A common-mode current is obtained from center tap 325 and filteredthrough center tap potential feed circuit 330. At output node 340, thevoltage across shunt resistor 350 from the applied filtered common-modecurrent is sampled and provided to the second receiver 372. The voltageV1 at output node 340 is used as a common-mode reference signal.

The first receiver 371 receives the combined differential andcommon-mode signal from the output winding of transformer 320. Thecommon-mode reference signal received at the second receiver 372 canthen be subtracted from the combined signal using DSP circuitry, asdiscussed above. The resulting signal is the differential signalcontaining only the communication data with minimal interference fromthe common-mode noise signal.

FIG. 4 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.Circuit 400 is substantially similar to circuit 300 of FIG. 3 with theaddition of direct current (DC) blocking capacitors 431 and 432 andcenter tap capacitor 435 in place of center tap potential feed circuit330. The first DC blocking capacitor 431 is coupled between the firstseries winding 311 and the input winding of transformer 320. Similarly,the second DC blocking capacitor 432 is coupled between the secondseries winding 312 and the input winding of transformer 320. The centertap capacitor 435 is coupled between center tap 325 and output node 340.

Series windings 311 and 312 together with center tap capacitor 435 andshunt resistor 350 form a low-pass filter that attenuates common-modeenergy to the input winding of transformer 320. Center tap capacitor 435has a construction that meets the safety isolation requirements forcommunication systems. In one embodiment, center tap capacitor 435 has acapacitance value in approximately a range of 1 nanofarad (nF) to 10 nF.In an alternative embodiment, center tap capacitor 435 has some othercapacitance value. As a result, when the common-mode current is sampledacross shunt resistor 350 on the low voltage side of center tapcapacitor 435, no additional high voltage isolation transformer isnecessary. Additionally, the resistance value of shunt resistor 350 islow enough to keep the combination of series windings 311 and 312 andcenter tap capacitor 435 functioning as an effective common-mode filterwith at least approximately 30 decibels (dB) of rejection. For example,shunt resistor 350 may have a value in approximately a range of 10 ohmsto 500 ohms. This maintains the necessary filtering on the input side oftransformer 320. Finally, as a result of common-mode impedance fromcenter tap capacitor 435, the filtered common-mode current will befrequency dependent and any common-mode current surges will be greatlyattenuated at output node 340, thus protecting the second receiver 372from saturation.

FIG. 5 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. Circuit 500 is substantially similar to circuit 300 of FIG. 3except that center tap potential feed circuit 530 is coupled between afirst primary winding 521 and a second primary winding 522 on an inputside of transformer 520. An output of center tap potential feed circuit530 is coupled to output node 340.

The functionality of circuit 500 is similar to that of circuit 300 ofFIG. 3 as well. A common-mode current is obtained from primary windings521 and 522 of transformer 520 and received by center tap potential feedcircuit 530. At output node 340, the voltage across shunt resistor 350from the applied filtered common-mode current is sampled and provided tothe second receiver 372. The voltage V1 at output node 340 is used as acommon-mode reference signal.

FIG. 6 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.Circuit 600 is substantially similar to circuit 500 of FIG. 5 exceptthat DC blocking capacitor 633 and center tap capacitors 636 and 637have replaced center tap potential feed circuit 530. DC blockingcapacitor 633 is coupled between the first primary winding 521 and thesecond primary winding 522 of transformer 520. Center tap capacitor 636is coupled between the first primary winding 521 and output node 340 andcenter tap capacitor 637 is coupled between the second primary winding522 and output node 340.

Center tap capacitors 637 and 638 operate to ground the electricalcenter of transformer 520. In one embodiment center tap capacitors 637and 638 are equal and have a capacitance value in approximately a rangeof 500 picofarads (pF) to 5 nF. In alternative embodiments, center tapcapacitors 637 and 638 have other values. In this embodiment, DCblocking capacitor 633 has a large capacitance value with respect tothat of center tap capacitors 637 and 638 and is in approximately arange of 15 nF to 68 nF. In alternative embodiments. DC blockingcapacitor 633 has some other value.

In this embodiment, the common-mode current is filtered by center tapcapacitors 637 and 638. The filtered common-mode current is then appliedto shunt resistor 350 and the voltage at output node 340 is sampled. Thevoltage signal V1 at output node 340 is provided to the second receiver372 as described above with respect to FIG. 3.

FIG. 7 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.Circuit 700 is substantially similar to circuit 600 of FIG. 6 with theaddition of differential impedance matching resistors 738 and 739. Afirst differential impedance matching resistor 738 is coupled betweenthe first primary winding 521 and the first center tap capacitor 636. Asecond differential impedance matching resistor 739 is coupled betweenthe second primary winding 522 and the second center tap capacitor 637.In one embodiment, impedance matching resistors 738 and 739 haveresistance values in approximately a range of 40 to 60 ohms. Inalternative embodiments, impedance matching resistors have other values.

In an alternative embodiment, the differential impedance matchingresistors are located on the output side of transformer 520. In eitherembodiment, the function of the circuit is the same. The filtered commonmode current is applied to shunt resistor 350 and the voltage at outputnode 340 is sampled. The voltage signal V1 at output node 340 isprovided to the second receiver 372.

FIG. 8 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. In this embodiment, circuit 800 includes input lines 801 and802, series windings 811 and 812, transformer 820, center tap potentialfeed circuit 830, output node 840, shunt resistor 850, low supply node860, receivers 871 and 872 and instant averager circuit 880. The firstseries winding 811 is coupled to the first input line 801 and isconfigured to receive a first input signal. The second series winding812 is coupled to the second input line 802 and is configured to receivea second signal. At the end opposite the first input line 801, the firstseries winding 811 is coupled to one end of an input winding oftransformer 820. Similarly, the second series winding 812 is coupled toa second end of the input winding of transformer 820. An output windingof transformer 820 is coupled to a first receiver 871. Center tappotential feed circuit 830 is coupled between center tap 825 on theinput side of transformer 830 and a low supply node.

In this embodiment, the common-mode current is received directly fromsignal lines 801 and 802. Instant averager circuit 880 is coupled to thefirst signal line 801 and the second signal line 802 and receives aportion of the common-mode current. The output of instant averagercircuit 880 is coupled to output node 840. Output node 840 is furthercoupled to a low supply node 860 through shunt resistor 850. In thisembodiment, low supply node 860 has a ground potential. In alternativeembodiments, low supply node 860 has some other low potential value.Also connected to output node 840 is a second receiver 872. Both thefirst receiver 871 and the second receiver 872 are referenced to ground.

A common-mode current is obtained from input lines 801 and 802 andfiltered through instant averager circuit 880. At output node 840, thevoltage across shunt resistor 850 from the applied filtered common-modecurrent is sampled and provided to the second receiver 872. The voltageV1 at output node 840 is used as a common-mode reference signal.

The first receiver 871 receives the combined differential andcommon-mode signal from the output winding of transformer 820. Thecommon-mode reference signal received at the second receiver 872 can besubtracted from the combined signal using DSP circuitry. The resultingsignal is the differential signal containing only the communication datawith minimal interference from the common-mode noise signal.

FIG. 9 illustrates a schematic diagram of a common-mode reference signalgeneration circuit according to one embodiment of the present invention.Circuit 900 is substantially similar to circuit 800 of FIG. 8 except forthe addition of DC blocking capacitors 931 and 932, center tap capacitor935 in place of center tap potential feed circuit 830 and isolationcapacitors 981 and 982 and matched resistors 983 and 984 in place ofinstant averager circuit 880. The first DC blocking capacitor 931 iscoupled between the first series winding 811 and the input winding oftransformer 820. Similarly, the second DC blocking capacitor 932 iscoupled between the second series winding 912 and the input winding oftransformer 820. The center tap capacitor 935 is coupled between thecenter tap 825 and low supply node 961. In this embodiment low supplynode 961 has a ground potential, however in alternative embodiments lowpotential node 961 has some other low potential value.

In this embodiment, the first isolation capacitor 981 is coupled toinput line 801 and the second isolation capacitor 982 is coupled toinput line 802. The first matched resistor 983 is coupled betweenisolation capacitor 981 and output node 840 and the second matchedresistor 984 is coupled between isolation capacitor 982 and output node840. In this embodiment, matched resistors 983 and 984 have resistancevalues in a range of approximately 5,000 ohms to 10,000 ohms and arematched to within approximately 1%, allowing a common-mode todifferential ratio of approximately 34 dB. In an alternative embodimentwhere matched resistors 983 and 984 are matched to within 0.1%,approximately 54 dB may be achieved. In another alternative embodiment,matched resistors 983 and 984 are matched to within some other thresholdvalue. In an alternative embodiment, matched resistors 983 and 984 havesome other resistance value. In this embodiment, isolation capacitors981 and 982 have a capacitance value of approximately 100 pF and aresafety-class capacitors that span the TNV-to-SELV barrier and provideisolation. In an alternative embodiment, isolation capacitors 981 and982 have some other capacitance value. Since isolation capacitor 981 andmatched resistor 983 and isolation capacitor 982 and matched resistor984 are coupled in series, in an alternative embodiment, the order isreversed. In other words, matched resistors 983 and 984 are coupled toinput lines 801 and 802 respectively with isolation capacitors 981 and982 coupled between matched resistors 983 and 984 and output node 840.

In this embodiment, shunt resistor 850 has a resistance in approximatelya range of 10 ohms to 1000 ohms. In an alternative embodiment, shuntresistor 850 has some other resistance value. Shunt resistor 850,together with matched resistors 983 and 984, form a summer with respectto ground which contains the common-mode information. The summer, alongwith isolation capacitors 981 and 982 form an attenuator that scales thecommon-mode signal to approximately −30 dB. The common-mode filterformed by the components of the instant averager circuit has relativelyhigh impedance for xDSL frequencies. As a result, no differentialloading effects are suffered. Due to the relative high impedance ofcapacitors 981 and 982 with respect to voice-band frequencies, arequired voice-band common mode balance of greater than 60 dB ismaintained.

In the operation of circuit 900, the common-mode current is filtered byisolation capacitors 981 and 982 and matched resistors 983 and 984. Thefiltered common-mode current is then applied to shunt resistor 850 andthe voltage at output node 840 is sampled. The voltage signal V1 atoutput node 840 is provided to the second receiver 872 as describedabove with respect to FIG. 8.

FIG. 10 illustrates a schematic diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. Circuit 10 is substantially similar to circuit 900 of FIG. 9except that the components of the center tap potential feed circuit arecoupled between a first primary winding 1021 and a second primarywinding 1022 on an input side of transformer 1020. In this embodiment,center tap potential feed circuit is made up of DC blocking capacitor1033 and center tap capacitors 1036 and 1037. DC blocking capacitor 1033is coupled between the first primary winding 1021 and the second primarywinding of transformer 1020. Center tap capacitor 1036 is coupledbetween the first primary winding 1021 and low supply node 961 andcenter tap capacitor 1037 is coupled between the second primary winding1022 and low supply node 961. The components of the center tap potentialfeed circuit serve to dump the common-mode energy of the received inputsignals to ground. Absence of the center tap potential feed circuitwould result in excess common-mode energy leaking across transformer1020 to receiver 872.

The operation of circuit 1000 is substantially similar to that discussedabove regarding circuit 900 of FIG. 9. The common-mode current isfiltered by isolation capacitors 981 and 982 and matched resistors 983and 984. The filtered common-mode current is then applied to shuntresistor 850 and the voltage at output node 840 is sampled. The voltagesignal V1 at output node 840 is provided to the second receiver 872.

FIG. 11 illustrates a schematic diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. Circuit 1100 is substantially similar to circuit 1000 of FIG.10 with the addition of differential impedance matching resistors 1138and 1139. A first differential impedance matching resistor 1138 iscoupled between the first primary winding 1021 and the first center tapcapacitor 1036. A second differential impedance matching resistor 1139is coupled between the second primary winding 1022 and the second centertap capacitor 1037.

In an alternative embodiment, the differential impedance matchingresistors are located on the output side of the transformer 1020. Ineither embodiment, the operation of the circuit is the same. Thefiltered common-mode current is applied to shunt resistor 850 and thevoltage at output node 840 is sampled. The voltage signal V1 at outputnode 840 is provided to the second receiver 872.

FIG. 12 illustrates a schematic block diagram of a common-mode referencesignal generation circuit according to one embodiment of the presentinvention. Circuit 1200 is substantially similar to circuit 800 of FIG.8 with the addition of signal filter 1290. Signal filter 1290 is coupledbetween output node 840 and receiver 872. Signal filter 1290 may be alow-pass filter, band-pass filter, or other filter type. In oneembodiment, signal filter 1290 is a second order filter with roll-offstarting at approximately 5 MHz. The common-mode reference signal V1 isapplied to signal filter 1290 so as to reduce high frequency content.Signal filter 1290 serves to prevent aliasing in the signal andoverloading of receiver 872.

Some portions of the above description are presented in terms ofalgorithms and symbolic representations of operations on data that maybe stored within a memory and operated on by a processor. Thesealgorithmic descriptions and representations are the means used by thoseskilled in the art to effectively convey their work. An algorithm isgenerally conceived to be a self-consistent sequence of acts leading toa desired result. The acts are those requiring manipulation ofquantities. Usually, though not necessarily, these quantities take theform of electrical or magnetic signals capable of being stored,transferred, combined, compared, and otherwise manipulated. It hasproven convenient at times, principally for reasons of common usage, torefer to these signals as bits, values, elements, symbols, characters,terms, numbers, parameters, or the like.

The above description includes several modules which may be implementedby hardware components, such as logic, or may be embodied in machineexecutable instructions, which may be used to cause a general-purpose orspecial-purpose processor programmed with the instructions to performthe operations described herein. Alternatively, the operations may beperformed by a combination of hardware and software.

In one embodiment, the methods described above may be embodied onto amachine-readable medium. A machine-readable medium includes anymechanism that provides (e.g., stores and/or transmits) information in aform readable by a machine (e.g., a computer). For example, amachine-readable medium includes read only memory (ROM); random accessmemory (RAM); magnetic disk storage media; optical storage media; flashmemory devices; DVD's, or any type of media suitable for storingelectronic instructions. The information representing the apparatusesand/or methods stored on the machine-readable medium may be used in theprocess of creating the apparatuses and/or methods described herein.

While some specific embodiments of the invention have been shown theinvention is not to be limited to these embodiments. The invention is tobe understood as not limited by the specific embodiments describedherein, but only by the scope of the appended claims.

What is claimed is:
 1. An apparatus comprising: a common-mode currentsensing circuit configured to receive a common-mode current; a shuntresistor coupled between the common-mode current sensing circuit and afirst low supply node and wherein the common-mode current sensingcircuit comprises an instant averager circuit and receives thecommon-mode current from a pair of signal lines, the pair of signallines comprising a first signal line and a second signal line.
 2. Theapparatus of claim 1, wherein the instant averager circuit comprises: afirst isolation capacitance or resistance coupled to the first signalline; a first of the other of a matched resistance or capacitancecoupled to the first isolation capacitance or resistance; a secondisolation capacitance or resistance coupled to the second signal line;and a second of the other of a matched resistance or capacitance coupledto the second isolation capacitance or resistance.
 3. The apparatus ofclaim 2, wherein a first end of the shunt resistor is coupled to thefirst matched resistor and the second matched resistor and a second endof the shunt resistor is coupled to the first low supply node.
 4. Theapparatus of claim 1, wherein the instant averager circuit comprises: afirst matched resistance coupled to the first signal line; a firstisolation capacitance coupled to the first matched resistance; a secondmatched resistance coupled to the second signal line; and a secondisolation capacitance coupled to the second matched resistance.
 5. Theapparatus of claim 4, wherein a first end of the shunt resistor iscoupled to the first isolation capacitance and the second isolationcapacitance and a second end of the shunt resistor is coupled to thefirst low supply node.
 6. The apparatus of claim 2, wherein the shuntresistor has a resistance in approximately a range of 10 ohms to 1000ohms.
 7. The apparatus of claim 2, further comprising: a first serieswinding coupled to the first signal line; a second series windingcoupled to the second signal line; and a transformer coupled to thefirst series winding and the second series winding.
 8. The apparatus ofclaim 7, wherein the transformer has a center tap on an input side. 9.The apparatus of claim 8, further comprising: a center tap potentialfeed circuit coupled between the center tap and a second low supplynode.
 10. The apparatus of claim 7, wherein the transformer has a firstprimary winding and a second primary winding on an input side.
 11. Theapparatus of claim 8, further comprising: a center tap potential feedcircuit coupled between the first primary winding, the second primarywinding and a second low supply node.
 12. The apparatus of claim 7,further comprising: a first receiver coupled to an output side of thetransformer; and a second receiver coupled to a node between the instantaverager circuit and the shunt resistor.
 13. The apparatus of claim 12,further comprising: a signal filter coupled between the node and thesecond receiver.
 14. A method, comprising: receiving a common-modecurrent at a common-mode sensing circuit; and sampling the common-modecurrent at a node coupled between the common-mode current sensingcircuit and a shunt resistor to generate a common-mode reference signalwherein receiving the common-mode current comprises receiving thecommon-mode current from a pair of signal lines, and wherein thecommon-mode current sensing circuit comprises an instant averagercircuit, the instant averager circuit coupled to the pair of signallines.
 15. The method of claim 14, wherein the shunt resistor has aresistance in approximately a range of 10 ohms to 1000 ohms.
 16. Theapparatus of claim 1, wherein the common-mode current sensing circuitcomprises an instant averager circuit.
 17. The apparatus of claim 16,wherein the common-mode current is received from a pair of signal linesand wherein the instant averager circuit is coupled to the pair ofsignal lines.